This paper develops an enhanced harmonic voltage compensator which is implemented with the aid of two repetitive controllers (RCs) in order to improve the output voltage performance of standalone distributed generation (DG) systems. The proposed harmonic voltage compensator is able to maintain the DG output voltage sinusoidal regardless of the use of nonlinear and/or unbalanced loads in the load side. In addition, it can offer good steadystate performance under various types of loads and a very fast dynamic response under load variations to overcome the slow dynamic response issue of the traditional RC. The feasibility of the proposed control strategy is verified through simulations and experiments.
I. INTRODUCTION
In recent decades, concerns about global warming, gas emissions and the depletion of fossil fuels have resulted in increasing utilization of renewable energy sources (such as wind turbines, photovoltaic, fuel cells, etc.) to produce electricity. Nowadays, a large number of renewable energy sources have been integrated into power distribution systems through power electronic converters in the form of distributed generation (DG)
[1]
. The DG systems are mainly developed for gridconnected operation with various operational functions such as power control, harmonic current mitigation, and reactive power compensation
[2]

[4]
. However, due to the demand for supplying electricity to rural villages and remote islands, the use of DG in standalone operation is also important. In standalone mode, DGs must deliver a sinusoidal voltage to loads at the point of common coupling (PCC) with a constant magnitude and frequency. Due to the absence of a stiff grid in the standalone operation of a DG system, the quality of the DG output voltage strongly depends on the performance of the voltage control strategy. The quality of the DG output voltage is mainly evaluated by the steadystate error and dynamic performance under load changes. In addition, with the wide use of nonlinear and unbalanced loads, the total harmonic distortion (THD) should also be considered to evaluate the DG output voltage performance.
Configuration of a standalone DG system connected with loads at the PCC.
The configuration of a standalone DG system connected with loads at the PCC is shown in
Fig. 1
. In order to supply a high quality output voltage (
v_{L}
) at the PCC, many control efforts have been developed
[5]

[15]
. For the case of balanced linear loads, a proportionalintegral (PI) controller in the synchronous reference frame is sufficient to produce a sinusoidal output voltage at the PCC
[5]

[7]
. However, the PI controller is unable to maintain a sinusoidal DG output voltage when unbalanced and/or nonlinear loads are connected to the PCC due to its limitation of the controlbandwidth. In order to overcome this issue, several advanced control methods have been proposed such as PI controllers in multiple reference frames
[8]
,
[9]
, predictive control
[10]
,
[11]
, adaptive control
[12]
, multiple resonant controllers
[13]
,
[14]
, and repetitive control
[15]
.
In
[8]
,
[9]
, to supply a pure sinusoidal output voltage at the PCC under a nonlinear load, a bank of PI controllers was used where each PI controller regulated the magnitude of a single harmonic voltage. In these control methods, many PI controllers and coordinate transformations are required to compensate all of the voltage harmonics, which makes this type of control strategy too complex. Meanwhile, a predictive control strategy was proposed in
[10]
which can provide a good control performance and a fast dynamic response. However, it is wellknown that the performance of a predictive controller depends heavily on knowledge of the system parameters. Hence, system uncertainties would be a vital issue affecting the control accuracy. An adaptive control strategy is introduced in
[12]
where a load current observer is developed to estimate the load current variations, which helps improving the dynamic performance of the voltage controller. However, even though the load current measurement is omitted, the inverter current measurement is required. Moreover, regardless of the control effort, the output voltage is disturbed under load step changes. A control method which uses multiple resonant controllers for handling unbalanced and nonlinear loads has been developed for DG systems
[13]
,
[14]
. By implementing the control scheme in the stationary reference frame, coordinate transformations are eliminated. However, since each resonant controller is capable of compensating only one specific harmonic voltage, a large number of resonant controllers must be used if all of the harmonic voltages need to be compensated. In addition, these control strategies have a current control loop and require load current measurements, resulting in a complex control scheme.
To overcome the complexity of multiple resonant controllers, an advanced control strategy with a repetitive controller (RC) was introduced in
[15]
. In
[15]
, one RC is able to replace a bank of resonant controllers. As a result, the control strategy is simplified. The RC in
[15]
can offer good steadystate performance as well as a very fast dynamic response to overcome the slow dynamic response issue of traditional RCs
[16]
,
[17]
. However, the RC in
[15]
is only suitable for application to threephase nonlinear loads because it takes into account only the dominant harmonic components in threephase systems, i.e., (6
n
±1)th (
n
=1, 2, 3…). Hence, if singlephase nonlinear loads or unbalanced loads are used in the system, the performance of the control strategy is deteriorated due to the presence of other harmonic components such as third, ninth, fifteenth, etc.
In this paper, in order to overcome the drawback of previous RCs, an enhanced voltage control strategy is proposed which is composed of two repetitive controllers. In the proposed harmonic voltage compensator, one RC is designed in the rotating reference (
dq
) frame to compensate the (6
n
±1)th (
n
=1, 2, 3…) harmonics and the other RC is designed in the stationary reference (
α

β
) frame to compensate triplen harmonics such as the third, ninth, fifteenth, etc. As a result, the DG output voltage is regulated to be a sinusoidal waveform irrespective of the presence of singlephase and threephase nonlinear and/or unbalanced loads. The proposed control strategy can offer excellent steadystate performance of the DG output voltage under various load conditions as well as a fast dynamic response under load variations thanks to the short delay time of both RCs, which is only onesixth of fundamental period. The feasibility of the proposed control strategy is verified through simulations and experiments.
II. HARMONIC VOLTAGE COMPENSATION SCHEME
 A. Effects of nonlinear and unbalanced loads on the DG output voltage
Connection interface of a DG with various loads.
The connection interface of a DG with various types of loads, including singlephase and threephase nonlinear loads and/or unbalanced loads, is shown in
Fig. 2
. In
Fig. 2
,
R_{f}
and
L_{f}
are the resistance and inductance of the line impedance, respectively. Based on
Fig. 2
, the DG output voltage (
v_{L}
) can be calculated as:
where
v_{i}
=
v
_{i1}
is the output voltage of the inverter, which is assumed to have only the fundamental component (
v
_{i1}
), and
i_{L}
is the load current.
If nonlinear and unbalanced loads are connected in the load side, the load current draws harmonic currents into the system. Thus, the DG output voltage is determined by:
where
i_{L1}
and
i_{Lh}
are the fundamental and harmonic components of the load current, respectively.
As can be seen in (2), even though the inverter can generate a pure sinusoidal output voltage, the DG output voltage becomes distorted due to a harmonic voltage drop on the line impedance. Hence, in order to achieve a sinusoidal output voltage at the PCC, the inverter must generate a distorted voltage to compensate for the harmonic voltage drop on the line impedance as follows:
where
v_{ih}
is the harmonic component of the inverter output voltage.
Theoretically, the inverter voltage
v_{i}
in (3) produces all of the harmonic components (odds and evens). However, in a practical system, the harmonic components are mainly composed of odd orders such as the third, fifth, seventh, ninth, etc. Hence, to produce a sinusoidal voltage at the PCC, the voltage compensator only needs to regulate these odd harmonics. The proposed harmonic voltage compensator composed of two repetitive controllers can fulfill the demand to supply a sinusoidal DG output voltage regardless of the use of singlephase nonlinear, threephase nonlinear and unbalanced loads.
 B. Harmonic Voltage Compensation Scheme
A block diagram of the proposed harmonic voltage compensator is shown in
Fig. 3
. This compensator consists of two repetitive controllers: RC1 and RC2. In
Fig. 3
, RC1 is implemented in the synchronous reference (
d

q
) frame rotating at the fundamental frequency
w
_{0}
to compensate the (6
n
±1)th (
n
=1, 2, 3…) harmonics whereas RC2 is designed in the stationary reference (
α

β
) frame to mitigate triplen (such as the third, ninth, fifteenth, etc.) harmonics. Thereby, the use of two repetitive controllers, RC1 and RC2, is sufficient to compensate all of the odd harmonic voltage drops caused by many kinds of loads to ensure that the DG output voltage is maintained sinusoidal.
Block diagram of the proposed harmonic voltage compensator.
III. PROPOSED REPETITIVE CONTROLLER
 A. Structure of the Repetitive Controller
General structure of a repetitive controller.
Fig. 4
shows the general structure of a RC in the discretetime domain. Based on
Fig. 4
, the transfer function of the RC can be described as:
where
z^{N}
is the time delay unit,
z^{k}
is the phase lead term,
Q
(
z
) is a filter transfer function,
K_{r}
is the RC gain,
R
(
z
) is the reference value,
E
(
z
) is the tracking error, and
U
(
z
) is the output of the RC.
In (4),
N
is the number of samples in one fundamental period which is defined as the ratio of the sampling frequency and the fundamental output frequency. As a result, the RC has three main components that need to be determined, i.e., the filter
Q
(
z
), the phase lead term
z^{k}
, and the RC controller gain
K_{r}
In
[15]
, the RC considers only the (6
n
±1)th (
n
=1, 2, 3…) harmonic components, which are the dominant components in threephase systems. To compensate the (6
n
±1)th harmonics, the RC in
[15]
is designed in the
dq
frame because in this frame the (6
n
±1)th harmonics behave as 6
n
th (
n
=1, 2, 3…) harmonics. The transfer function of the RC in
[15]
is shown as:
As presented in
[15]
, the RC offers good steadystate performance and a fast dynamic response under threephase nonlinear load conditions. However, if singlephase nonlinear loads or unbalanced loads are used in the system, the control performance will be deteriorated due to the presence of triplen harmonic components such as the third, ninth, fifteenth, etc. In order to compensate the odd harmonic components, the traditional RC or the oddharmonic RC is an effective solution
[16]
,
[17]
. Unfortunately, these RCs have a long delay time, which normally results in a poor dynamic response under load variations.
 B. Proposed Repetitive Controller
In order to compensate the odd harmonic components with a fast dynamic response, this paper introduces an enhanced harmonic voltage compensator composed of two different RCs where one RC is designed to compensate the (6
n
±1)th (
n
=1, 2, 3…) harmonic components and the other RC is used to compensate triplen harmonics such as the third, ninth, fifteenth, etc.
Bode diagram of the RC1 and RC2.
To compensate the (6
n
±1)th (
n
=1, 2, 3…) harmonics, RC1 is designed in the
d

q
frame and has the same transfer function as given in (5). On the other hand, the ohter repetitive controller, i.e., RC2, is designed in the
α

β
frame to mitigate triplen harmonics. The transfer function of RC2 is given as:
As a result, with the combination of two repetitive controllers, RC1 and RC2, designed in different reference frames, all of the odd harmonics can be compensated to supply a sinusoidal DG output voltage. As given in (5) and (6), the number of the sampling delay of the two RCs is limited at onesixth when compared to that of the traditional RC given in (4). Therefore, with the proposed controller, a fast dynamic response of can be achieved, which is similar to the RC in
[15]
, without degrading the control performance under singlephase nonlinear load or unbalanced load conditions.
Bode diagrams of RC1 and RC2 are shown in
Fig. 5
(a) and
Fig. 5
(b), respectively. In
Fig. 5
, the fundamental frequency is selected at 50 Hz. As shown in
Fig. 5
, RC1 in the
d

q
frame provides a high controller gain at the 6
n
th (
n
=1, 2, 3…) harmonics, meanwhile RC2 in the
α

β
frame has a high gain at triplen harmonics. Therefore, a combination of these two repetitive controllers ensures that the odd harmonics can be effectively compensated.
In (5) and (6),
Q
(
z
) is used to improve the system stability margin by reducing the peak gains of the RC at the highfrequency range.
Q
(
z
) is regularly employed with a zero phaseshift lowpass filter (LPF) as given in (7) because this can improve the stability margin without degrading the steadystate performance of the RC.
where
α
_{0}
+ 2
α
_{1}
= 1 and
α
_{0}
,
α
_{1}
> 0 .
In order to investigate the stability condition of the proposed RC, the relationship between the tracking error
E
(
z
), the reference
R
(
z
), and the disturbance
D
(
z
) is derived as (8) according to
Fig. 4
.
Let
H
(
z
) =
Q
(
z
)
K_{r}z^{k}G_{P}
(
z
). Then, the repetitive control system becomes stable if the condition given in (9) is satisfied
[16]
.
where
w
∈[0,
π
/
T
] ;
T
denotes the sampling period and
π
/
T
is the Nyquist frequency.
According to (9), the stability condition of the RC does not depend on the number of the delay sample
N
, but relies on
Q
(
z
),
z^{k}
, and
K_{r}
. In order to guarantee the stability of the repetitive control system, the parameters
Q
(
z
),
z^{k}
, and
K_{r}
should be determined so that the vector
H
(
e^{jwT}
) does not exceed the unity circle. This condition should be taken into account when designing the RC.
IV. DESIGN OF THE REPETITIVE CONTROLLER
The basic process to design a RC has been presented in previous studies
[15]

[17]
. In order to ensure the robust operation of an RC, three components need to be designed: the filter
Q
(
z
), the phase lead term
z^{k}
, and the RC controller gain
K_{r}
. These components are determined based on the system parameters given in
Table I
.
Bode diagram of G_{P}(z)z^{k} with different values of k.
Loci of vector H(e^{jwT}) with different values of K_{r}.
In terms of the filter
Q
(
z
), a zero phaseshift LPF with the transfer function given in (10) is selected because it provides a cutoff frequency of about 2660 Hz which is sufficient to compensate the harmonic components up to the 51
^{st}
order.
The phase lead term
z^{k}
is used to compensate the phase lag induced by the plant
G_{P}
(
z
); and
k
is selected to the minimize the phase displacement of
G_{P}
(
z
)
z^{k}
. If the output of a DG is considered to be an ideal voltage source, the plant can be simplified as a
LC
filter with the transfer function as:
SYSTEM PARAMETERS
Fig. 6
shows a Bode diagram of
G_{P}
(
z
)
z^{k}
with different values of
k
. In
Fig. 6
,
k
=3 is selected because it provides a minimum phase displacement at the dominant harmonic components up to the order 31
^{st}
. In addition, if one extra delay sample caused by the computation time of the control strategy is considered,
k
=4 is selected.
In the next step, the controller gain
K_{r}
is determined to satisfy the stability condition given in (9) and to ensure the robust operation of the RC. To select a proper value for
K_{r}
, the loci of the vector
H
(
e^{jwT}
) is shown in
Fig. 7
with different values of
K_{r}
. It can be observed that the vector
H
(
e^{jwT}
) is located inside the unity circle, which means that the system is stable if
K_{r}
is less than 1.8. In fact, a large
K_{r}
offers better steadystate performance as well as a faster response. However, it limits the stability margin of the system at the same time. Therefore, in order to guarantee a sufficient stability margin,
K_{r}
=1.5 is selected.
V. SIMULATION RESULTS
A simulation model of a DG was built by PSIM to verify the effectiveness of the proposed compensator. The detailed system parameters are given in
Table I
. In the simulation, three test cases are considered:

 Case I: a threephase diode rectifier is used in the load side.

 Case II: a singlephase diode rectifier is connected between phase A and B.

 Case III: both singlephase and threephase diode rectifiers are used (Case I + Case II).
These three test cases are carried out by using the previous RC introduced in
[15]
which compensates only the (6
n
±1)th harmonic components and the proposed control strategy to compare their control performance.
Fig. 8
shows the steady state performance of the DG output voltage (
v_{L,abc}
) and load current (
i_{L,abc}
) under the three test cases by using the previous RC introduced in
[15]
. As shown in
Fig. 8
, the previous RC is only able to offer good performance of the DG output voltage when a threephase diode rectifier is used, case I, in
Fig. 8
(a). In the other test cases, it fails to maintain a sinusoidal output voltage at the PCC. This is because the previous RC takes into account only the (6
n
±1)th harmonics, while triplen harmonic components (such are third, ninth, fifteen, etc) caused by a singlephase nonlinear load cannot be compensated properly. As a result, the DG output voltages are distorted as shown in
Fig. 8
(b) and (c).
Steadystate performance of the DG output voltage and load current with the previous RC under (a) case I, (b) case II, (c) case III.
Steadystate performance of the DG output voltage and load current with the proposed control strategy under (a) case I, (b) case II, (c) case III.
A simulation of the DG with the proposed control strategy under the same load condition as
Fig. 8
was carried out and the results are shown in
Fig. 9
. In
Fig. 9
, it is obvious that the proposed control strategy can provide good performance of the DG output voltage in all three test cases. This is because the proposed controller produces a high controller gain at the (6
n
±1)th harmonics as well as triplen. As a result, it is able to effectively compensate all of the odd harmonic voltage drops and regulate the DG output voltage to be sinusoidal under various load conditions.
Dynamic response of the DG when the load is changed with (a) the oddharmonic RC, (b) the proposed control strategy.
Along with a good steadystate performance, a fast dynamic response under load variations is also a crucial factor for a DG system. The dynamic response of the DG output voltage by using an oddharmonic RC
[17]
and the proposed control strategy under a load step change is shown in
Fig. 10
. In
Fig. 10
(a), during load changes, the oddharmonic RC needs more than 90ms to regain a sinusoidal DG output voltage. Since the oddharmonic RC has a delay time of half a fundamental cycle, it usually needs several fundamental cycles to settle at the steadystate condition after load changes. Meanwhile, in
Fig. 10
(b), the proposed controller provides a much faster dynamic response. The tracking error becomes almost zero and the DG output voltage can be recovered to be a sinusoidal waveform within about 20ms (one fundamental cycle). From the simulated results, it can be concluded that the proposed controller offers excellent steadystate performance under various load conditions as well as a very fast dynamic response during load variations.
SUMMARRY OF THD VALUE OF DG OUTPUT VOLTAGE
SUMMARRY OF THD VALUE OF DG OUTPUT VOLTAGE
A summary of the THD value of the DG output voltage with the previous RC and the proposed control strategy are shown in
Table II
. It can be seen that the proposed control strategy provides a much better performance when compared to the previous RC. The proposed control strategy is always able to keep the THD value of the DG output voltage lower than 1% in all test cases. In contrast, the previous RC can only provide a low THD in case I. It provides very high THD values in case II and case III. Therefore, the proposed control strategy is more general and is more effective under various load conditions.
VI. EXPERIMENTAL RESULTS
An overview of the experimental system is shown in
Fig. 11
. All of the parameters in the experimental system are the same as the simulation model given in
Table I
. The control strategy is carried out by using a floatingpoint DSP (TMS320F28335 by Texas Instruments). The same three mentioned test cases are carried out experimentally to verify the effectiveness of the proposed control strategy.
Experimental system of the DG.
In
Fig. 12
, the experimental results with the previous RC
[15]
are shown. According to
Fig. 12
, which corresponds to the simulation results shown in
Fig. 8
, the DG output voltage is maintained balanced and sinusoidal only under case I, i.e., the threephase nonlinear load. In the other cases, the DG output voltages become distorted and unbalanced due to the existence of the singephase diode rectifier. The presence of triplen harmonics causes the voltage to become distorted and unbalanced because the previous RC can only compensate the (6
n
±1)th harmonics. As a result, the previous RC is unable to provide good control performance under unbalanced nonlinear load conditions.
Steadystate performance of the DG output voltage and load current with the previous RC under (a) case I, (b) case II, (c) case III.
In contrast, the proposed control strategy effectively regulates the DG output voltage to be sinusoidal in all of the test cases shown in
Fig. 13
. Since the proposed controller is designed to compensate all of the odd harmonics, the DG output voltage is maintained sinusoidal irrespective of the existence of singlephase or threephase nonlinear loads. The experimental results coincide very well with those of the simulation.
Steadystate performance of the DG output voltage and load current with the proposed control strategy under (a) case I, (b) case II, (c) case III..
Along with an improved steadystate performance, the proposed control scheme also offers a fast dynamic response under load step changes. The dynamic response of the DG output voltage using the oddharmonic RC
[17]
and the proposed control strategy under load variations is shown in
Fig. 14
. In
Fig. 14
(a), when the load changes, the oddharmonic RC needs about 100ms (five fundamental cycles) to regain a sinusoidal DG output voltage. Meanwhile, in
Fig. 14
(b), the proposed controller only needs about 30 ms to make the DG output voltage settle at the steadystate performance after load changes. The fast dynamic response of the proposed harmonic voltage compensator can be seen experimentally.
Dynamic response of the DG when the load is changed with (a) the oddharmonic RC (b) the proposed control strategy.
VII. CONCLUSIONS
This paper proposed an enhanced harmonic voltage compensator for standalone DG systems which is composed of two RCs. The analysis and design of the two RCs were presented in detail in this paper. By designing one RC to regulate the (6
n
±1)th harmonics and the other RC to compensate triplen harmonics, the proposed RC is capable of compensating all of the odd harmonics with a faster dynamic response when compared to the traditional RC. As a result, the proposed compensator provides excellent steadystate performance as well as a very fast dynamic response. The feasibility of the proposed control strategy is verified through simulations and experiments. The DG output voltage is regulated to be almost pure sinusoidal with an ultralow THD under various load conditions including singlephase and threephase nonlinear and unbalanced loads.
Acknowledgements
This work was supported by the National Research Foundation of Korea Grant funded by the Korean Government.
BIO
QuocNam Trinh was born in Thanh Hoa, Vietnam, in 1985. He received his B.S. in Electrical Engineering from the Ho Chi Minh City University of Technology, Ho Chi Minh City, Vietnam, in 2008. He is currently a combined M.S./Ph.D. student at the University of Ulsan, Ulsan, Korea. He is a member of the Korean Institute of Power Electronics (KIPE). His current research interests include distributed generation, active power filters, harmonic compensation, and power quality.
HongHee Lee received his B.S., M.S., and Ph.D. in Electrical Engineering from Seoul National University, Seoul, Korea, in 1980, 1982, and 1990, respectively. He is a Professor in the School of Electrical Engineering, University of Ulsan, Ulsan, Korea. He is also the Director of the Networkbased Research Center (NARC) at the University of Ulsan. His current research interests include power electronics, networkbased motor control, and control networks. He is a Member of the Institute of Electrical and Electronics Engineers (IEEE), the Korean Institute of Power Electronics (KIPE), the Korean Institute of Electrical Engineers (KIEE), and the Institute of Control, Automation, and Systems Engineers (ICASE).
TaeWon Chun was born in Korea in 1959. He received his B.S. in Electrical Engineering from Pusan National University, Pusan, Korea, in 1981, and his M.S. and Ph.D. in Electrical Engineering from Seoul National University, Seoul, Korea, in 1983 and 1987, respectively. Since 1986, he has been a Faculty Member in the Department ofElectrical Engineering, University of Ulsan, Ulsan, Korea, where he is currently a Full Professor. His current research interests include the control of electrical machines, power converter circuits, and industrial applications.
Borbely M.
,
Kreider J. F.
2001
Distributed Generation The Power Paradigm for the New Millennium.
CRC Press
Blaabjerg F.
,
Teodorescu R.
,
Liserre M.
,
Timbus A. V.
2006
“Overview of control and grid synchronization for distributed power generation systems”
IEEE Trans. Ind. Electron.
53
(5)
1398 
1409
DOI : 10.1109/TIE.2006.881997
Noroozian R.
,
Gharehpetian G.
,
Abedi M.
,
Mahmoodi M.
2010
“GridTied and standalone operation of distributed generation modules aggregated by cascaded boost converters”
Journal of Power Electronics
10
(1)
97 
105
DOI : 10.6113/JPE.2010.10.1.097
Marwali M. N.
,
Keyhani A.
2004
“Control of distributed generation systems–part I: voltages and currents control”
IEEE Trans. Power Electron.
19
(6)
1541 
1550
DOI : 10.1109/TPEL.2004.836685
Ko S.H.
,
Lee S.W.
,
Lee S.R.
,
Nayar C. V.
,
Won C.Y.
2009
“Design considerations for a distributed generation system using a voltagecontrolled voltage source inverter”
Journal of Power Electronics
9
(4)
643 
653
Teodorescu R.
,
Blaabjerg F.
2004
“Flexible control of small wind turbines with grid failure detection operating in standalone or gridconnected mode,”
IEEE Trans. Power Electron.
19
(5)
1323 
1332
DOI : 10.1109/TPEL.2004.833452
Chen Z.
,
Hu Y
,
Blaabjerg F.
2006
“Control of distributed power systems”
in Proceedings of IPEMC 06
1 
6
Patel H.
,
Agarwal V.
2008
“Control of a standalone inverterbased distributed generation source for voltage regulation and harmonic compensation”
IEEE Trans. Power Del.
23
(2)
1113 
1120
DOI : 10.1109/TPWRD.2007.915890
Palle S.
,
Arafat N.
,
Sozer Y.
,
Husain I.
“Voltage harmonic control of weak utility grid through distributed energy systems”
in Proc. IEEE Energy Conversion Congress and Exposition ECCE 2012
1520, Sep. 2012.
1982 
1989
Bahrani B.
,
Rufer A.
“Model predictivebased voltage regulation of an islanded distributed generation unit”
in Proc. IEEE Energy Conversion Congress and Exposition ECCE 2011
1720, Sep. 2011.
465 
472
Delghavi M. B.
,
Yazdani A.
2011
“IslandedMode Control of ElectronicallyCoupled Distributed Resource Units under Unbalanced and Nonlinear Load Conditions”
IEEE Trans. Power Del.
26
(2)
661 
673
DOI : 10.1109/TPWRD.2010.2084599
Dai M.
,
Marwali M. N.
,
Jung J. W.
,
Keyhani A.
2008
“A threephase fourwire inverter control technique for a single distributed generation unit in island mode”
IEEE Trans. Power Electron.
23
(1)
322 
331
DOI : 10.1109/TPEL.2007.911816
Do T.
,
Leu V.
,
Choi Y.
,
Choi H.
,
Jung J.
2013
“An adaptive voltage control strategy of threephase inverter for standalone distributed generation systems”
IEEE Trans. Ind. Electron.
60
(12)
5660 
5672
DOI : 10.1109/TIE.2012.2230603
Nian H.
,
Zeng R.
2011
“Improved control strategy for stand alone distributed generation system under unbalanced and non linear loads”
IET Renew. Power Gener
5
(5)
323 
331
DOI : 10.1049/ietrpg.2010.0216
Trinh Q. N.
,
Lee H. H.
2013
“An advanced repetitive controller to improve the voltage characteristics of distributed generation with nonlinear loads”
Journal of Power Electronics
13
(3)
409 
418
DOI : 10.6113/JPE.2013.13.3.409
Zhang K.
,
Kang Y.
,
Xiong J.
,
Chen J.
2003
“Direct repetitive control of SPWM inverters for UPS purpose”
IEEE Trans. Power Electron.
18
(3)
784 
792
DOI : 10.1109/TPEL.2003.810846
Zhou K.
,
Low K.S.
,
Wang D.
,
Luo F.L.
,
Zhang B.
,
Wang Y.
2006
“Zerophase oddharmonic repetitive controller for a singlephase PWM inverter”
IEEE Trans. Power Electron.
21
(1)
193 
201
DOI : 10.1109/TPEL.2005.861190