A novel miniaturized artificial magnetic conductor (AMC) is proposed for dualband operation. An AMC unit cell that employs four slots in the metallic patch is used to achieve miniaturization as well as easy control of the second/ first resonant frequency ratio, which can be varied from 1.5 to 3.26 by simply changing the slot shape for a given metallic patch size. A dualband antenna composed of a wideband monopole suspended over the proposed AMC surface is designed and tested to validate this approach. The measurements result in a satisfactory and good matching condition for the dualband antenna.
Ⅰ. Introduction
The artificial magnetic conductor (AMC) surface, also called the metasurface, highimpedance surface, or reactive impedance surface, has been widely used as an artificial ground plane or reflector to enhance performance of many different antenna types while achieving profile miniaturization
[1
,
2]
. An AMC works as a perfect magnetic conductor (PMC) at resonant frequencies with the 0° phase of the reflected wave when illuminated by a normally incident plane wave. Its bandwidth is defined as the frequency range over which the phase of the reflection coefficient is between ±90°
[2]
.
In many applications, an antenna works at different frequencies simultaneously
[3

10]
; consequently, the AMC requires multiband operation that can match with the antenna’s working frequencies. Several different AMC structures have been developed for dualband operation, including double bowties
[11]
, concentric squares
[12]
, or hexagonal patches
[13]
on a unit cell, in order to achieve dualband characteristics. In addition, a mushroomtype cell loaded with symmetric meandered slots has been applied as a dualband metasurface
[14]
. However, the lack of miniaturization means that most of these AMCs have a large unitcell size compared with the effective wavelength. A genetic algorithm has been used to develop multiband AMC surface designs by simultaneously optimizing the geometry and size of the unit cell
[15]
; however, these frequency bands are not easy to adjust independently. Dualfrequency operation can be achieved using two layers of a square patch with varactor diodes
[16]
or double patches incorporated with lumped capacitors
[17]
. However, both of these techniques increase the complexity and cost of the AMC.
In this paper, we describe a miniaturized dualband AMC structure that allows easy control of the second/first resonant frequency ratio; this is achieved by inserting four slots into the metallic patch of a unit cell. We demonstrated the dualband characteristics by fabricating and analyzing a wideband monopole suspended over the proposed AMC surface. The antenna over the AMC surface has measured impedance bandwidths of 2.372.59 GHz and 4.285.62 GHz for a —10 dB reflection coefficient and unidirectional radiation patterns. We used the ANSYS Ansoft highfrequency structure simulator (HFSS) in this study.
Ⅱ. Proposed AMC Design
Fig. 1
shows the unit cell of the initial AMC design, which is a twodimensional square metal patch structure printed periodically on a grounded substrate. The initial design, denoted as #1, was first proposed and analyzed in
[2]
. In the present paper, we undertake a brief inves tigation of its features. In the simulations, the unit cell was excited by a singlemode wave port at the top and subjected to a periodic boundary condition along the
x
 and
y
axes
[18]
. The resulting structure can be considered to behave as a parallel
LC
circuit in
Fig. 1
(b), where the edge coupling of the square patch functions as a shunt capacitor (
C
), while the shortcircuited dielectric loaded transmission line is modeled as a shunt inductor (
L
). Therefore, the resonant frequency of the circuit can be expressed as follows:
where
C
=
l_{eff}C_{0}
, with
l_{eff}
as the effective length of the square patch and
C_{0}
as the existence capacitor per unit length, determined based on the coplanar stripline modeling shown in
Fig. 1
(c). The variation in the patch size and the gap separation influences
L
, whereas the substrate thickness and permittivity mainly affect
C
; both parameters can be used to control the resonant frequency. The calculations of
L
and
C
have been detailed in
[2]
.
Initial artificial magnetic conductor design (#1): (a) unit cell, (b) equivalent circuit, and (c) coplanar stripline modeling for calculation of existence capacitor per unit length (C_{0}). PEC=perfect electrical conductor.
Previous research on this subject was concerned only with the primary resonant frequency for various design parameters of the unit cell. However, the use of the simulator to investigate the structure shown in
Fig. 1
reveals the existence of higher resonant frequencies, as shown in
Fig. 2
(a), which shows the simulated reflection phase of the initial AMC. Here, a unit cell of the initial design with a 9.6 mm
^{2}
square metallic patch was built on a grounded 10×10 mm RT/duroid 6010 (Rogers Corp., Roger, CT, USA) substrate having
ε_{r}
=10.2, tan
δ
=0.0023, and
h_{s}
=1.27 mm.
Fig. 2
(a) shows that the resulting structure had first and second resonant frequencies of 3.44 and 11.18 GHz, respectively. This result is depicted in
Fig. 2
(b), which shows the simulated surface current (
J_{sur}
) distribution on the patch at the first and second resonant frequencies. Standing waves appeared in the patch at both frequencies. Along the incident
E
field direction, 1/2 and 3/2 periods of the
J_{sur}
magnitude appeared at the first and second resonant frequencies, respectively. The patch size was therefore approximately equal to 0.5
λ_{eff}
for the first resonance and 1.5
λ_{eff}
for the second resonance, where
λ_{eff}
is the effective wavelength. This behavior is nearly identical to the resonance behavior of the square patch microstrip antenna that was investigated theoretically using several methods and verified experimentally in
[19]
.
(a) Simulated reflection phase of #1 and (b) its simulated surface current distribution on metallic patch at first and second resonance frequencies
(a) Unit cell of the #2 design, (b) effective patch length (l_{eff}), and (c) simulated reflection phase for artificial magnetic conductor without/with slots in metallic patch.
The capacitor (
C
) in the equivalent circuit of #1 can be adjusted simply by making suitable changes in the geometry of the periodic metallic sheet; consequently, the corresponding resonant frequencies can be modified and controlled
[15]
. Accordingly, the four slots are symmetrically inserted into the metallic patch of the initial AMC in
Fig. 3
(a), denoted as #2, to decrease the resonant frequencies for the same volume. Each slot was designed with a length and width of
L_{p}
and
W_{p}
, respectively.
Fig. 3
(b) shows that the effective length (
l_{eff}
) of the square patch increased significantly after the insertion of the slots, whereas
C_{0}
was hardly influenced by a
W_{p}
of less than
W
/10. Therefore, the capacitance (
C
=
l_{eff}C
_{0}
) increased, and consequently, the resonant frequencies decreased. This result can be observed definitively in
Fig. 3
(c), which shows the simulated reflection phases for #1 and #2. Each slot in #2 was designed with
L_{p}
=4 mm and
W_{p}
=0.5 mm.
Fig. 3
(c) shows that the first and second resonance frequencies of #2 were 3 and 8 GHz, respectively; these are considerably lower than the corresponding values for #1. We realized that the variation in the slot width (
W_{p}
) slightly affected the reduction in resonant frequency because
l_{eff}
depends only on the slot length (
L_{p}
). This result is also evident from
Fig. 4
, which shows that the variations in the slot length (
L_{p}
) and width (
W_{p}
) affected the reflection phase of #2. The first and second resonant frequencies decreased significantly as
L_{p}
increased in
Fig. 4
(a) but were unaffected by the changes in
W_{p}
in
Fig. 4
(b). However, the effect of
W_{p}
was not the same for all values of
L_{p}
. For example, when
W_{p}
was varied, the resonant frequencies of #2 barely changed for
L_{p}
values smaller than 3 mm. However, for
L_{p}
values greater than 3 mm, the first resonant frequency was only slightly affected, while the second resonant frequency increased significantly. We can understand that for a large
L_{p}
value, the first resonance is generated by the entire patch, whereas the second resonance occurs because of the four smaller squares located in the corners of the patch, as shown in
Fig. 5
. This concept has been proposed and investigated in
[15]
.
We further reduced and controlled the resonance frequencies by modifying the slots in the metallic patch of #2 into Tshapes, denoted as #3, as shown in
Fig. 6
(a). The #3 design is the proposed AMC structure optimized to obtain the first and second resonance at approximately 2.45 and 5.5 GHz, respectively. The optimized design parameters of each slot are as follows:
L_{p}
=1.6 mm,
W_{p}
=0.5 mm,
L_{s}
=5 mm,
W_{s}
=0.5 mm, and
L_{a}
=1.8 mm. The features of the proposed structure were almost the same as those of #2, but it yielded considerably lower resonance frequencies. This result can be observed in
Fig. 6
(c), which shows the simulated reflection phases for all steps of the AMC design process. Here, #2 was chosen with
W_{p}
=0.5 mm and
L_{p}
=4 mm. We can see that the resonant frequencies of #2 decreased significantly compared with those of #1, and its second/first resonant frequency ratio was approximately 2.67. The #3 design yielded considerably lower resonant frequencies than #2; its first and second resonance frequencies were 2.45 and 5.5 GHz, respectively, and the frequency ratio was approximately 2.24. The simulation shows that the proposed AMC yielded bandwidths of 2.422.48 GHz and 5.385.57 GHz for the ±90° reflection phase at its first and second resonance frequencies, respectively. These results indicate that miniaturization of the AMC unit cell was achieved by the insertion of slots into the metallic patch.
Simulated reflection phase of #2 with varying L_{p} and W_{p}: (a) L_{p} varied while W_{p}=0.5 mm, and (b) W_{p} varied while L_{p}=3 mm.
Simulated reflection phase of #2 for varying W_{p} while L_{p}=4 mm.
(a) Geometry of the proposed artificial magnetic conductor design #3 and (b) simulated reflection phase for all steps of design process.
Fig. 7
shows the simulated current distribution on the metallic patch surface of the #3 AMC at the first and second resonant frequencies. The first resonance is generated by the entire patch, whereas the second resonance is generated by the small section in the corners of the patch. The proposed AMC structure provides easy control over the second/first resonant frequency ratio because it retains the features of #2 with large
L_{p}
and has a coupling between the angled parts (
L_{a}
) of the two neighboring slots in the metallic patch. This feature is clearly observed in
Fig. 8
, which shows the simulated reflection phase for the different design parameters of the metallic patch of a unit cell that strongly affect the second/first resonant frequency ratio. In the simulation, one parameter is varied while the other parameters are fixed, similar to the case of #3.
Fig. 8
(a) shows that an increase in
W_{p}
from 0.1 to 0.5 mm in 0.2mm steps caused almost no change in the first resonant frequency, while the second resonant frequency increased significantly; consequently, the second/first resonant frequency ratio increased. An increase in
L_{p}
from 1.2 to 1.6 mm in 0.2mm steps decreased the first resonant frequency, while the second resonance frequency remained almost the same; consequently, the second/first resonant frequency ratio again increased in
Fig. 8
(b).
Fig. 8
(c) shows that a stepwise increment of 0.2 mm in
W_{s}
from 0.1 to 0.5 mm decreased the first resonant frequency, while the second one barely changed; consequently, the second/first resonant frequency ratio again increased. The HFSS simulations show that a metallic patch having dimensions of
W
=9.6 mm,
L_{p}
=1.4 mm,
W_{p}
=0.1 mm,
L_{s}
=4 mm,
W_{s}
=0.1 mm, and
L_{a}
=1.8 mm yielded the minimum second/first resonant frequency ratio of 1.5. The metallic patch without a slot, which was labeled #1, yielded the maximum second/first resonant frequency ratio of 3.26. Therefore, the proposed AMC can be easily applied to dualband operation by using its first and second resonance frequencies. In addition, the HFSS simulations show that the minimum frequency of 1.6 GHz in the first resonance can be achieved with
W
=9.6 mm,
L_{p}
=4.5 mm,
W_{p}
=0.1 mm,
L_{s}
=0.2 mm,
W_{s}
=0.1 mm, and
L_{a}
=6.4 mm. When compared with #1, which yielded the first resonant frequency of 3.44 GHz, the miniaturization factor is greater than two.
Surface current distribution on the metallic patch of the #3 artificial magnetic conductor unit cell at 2.45 GHz (a) and 5.5 GHz (b).
Simulated reflection phase of the artificial magnetic conductor structure for different design parameters of unit cell’s metallic patch: (a) W_{p}, (b) L_{p}, and (c) W_{s}.
Ⅲ. Measurements
Both a perfect electrical conductor (PEC) and a PMC surface are known to have a strong coupling with the antennas above them
[2]
. When the antenna is placed in close proximity and parallel to a PEC, its impedance matching is rather difficult. In contrast, the impedance matching of the antenna in close proximity to a PMC appears to be easier. Accordingly, the antenna system was designed to prove that the proposed AMC worked as a PMC at the resonance frequencies. We confirmed the features of the proposed AMC shown in
Fig. 6
by designing, fabricating, and measuring a dualband antenna (
Fig. 9
). A 10×10 cell array of #3 described in the previous section was chosen to form an AMC surface with overall size of 100 mm×100 mm×1.27 mm. A wideband monopole antenna was suspended 6 mm above the AMC using ROHACELL structural foam (Evonik Industries, Essen, Germany) having
ε_{r}
=1.07 and tan
δ
=0.0006. A wideband monopole that was fed by a 50Ω microstrip line was fabricated on both sides of an RT/duroid 5880 (Rogers Corp.) substrate having
ε_{r}
=2.2, tan
δ
=0.0009, and thickness=0.7874 mm. An Agilent N5230A network analyzer and a 3.5mm coaxial calibration standard GCS35M were used to conduct measurements on the prototype (
Fig. 10
). The monopole antenna was tested in free space and over a 100 mm×100 mm copper plate and AMC surface at a height of 6 mm.
Fig. 11
shows the simulated and measured reflection coefficients of a monopole with different reflectors and shows a good agreement between the two. In free space, the antenna yielded a measured impedance matching bandwidth of 1.976.34 GHz for the —10 dB reflection coefficient, while the simulated bandwidth was 1.96.8 GHz. For the antenna over the copper plate, both simulations and measurements showed that the antenna did not match well in the region near the 2.4 GHz but yielded a good match around 6 GHz. The antenna over the AMC yielded measured impedance bandwidths of 2.372.59 GHz and 4.285.62 GHz, while the simulated bandwidths were 2.402.58 GHz and 4.375.50 GHz. The first and second bands of the antenna system verified the dualband capability of the proposed AMC. The impedance bandwidth became narrower after loading the AMC because the bandwidth of the antenna system depended on the operation bandwidth of the AMC.
The radiation patterns were measured in a full anechoic chamber of dimensions 15.2 m×7.9 m×7.9 m.
Fig. 12
shows the simulated and measured radiation patterns of the monopole antenna in free space and over the AMC surface at 2.45 and 5.2 GHz. The measurements agreed rather closely with the simulations. When compared with the antenna in free space, the gain of the antenna over the AMC surface increased in the forward direction by approximately 6 and 4 dB at the lower and upper frequencies, respectively. The antenna over the AMC yielded backradiation reductions of 15 and 20 dB at 2.45 and 5.2 GHz, respectively, when compared with the antenna in free space. The radiation patterns at the upper frequency were not quite symmetric because of the monopole antenna’s geometry. Additionally, the ripples in the measured radiation patterns could be attributed to the effects of the foam rack and the tape used to fix the antenna into the measurement setup. These results indicate that the monopole over the AMC surface yielded a unidirectional radiation pattern with high front toback ratio in both bands.
(a) Wideband monopole antenna (units in mm) and (b) monopole antenna over the artificial magnetic conductor (AMC) surface.
Fabricated dualband monopole antenna over the artificial magnetic conductor surface.
Comparison of reflection coefficients of a wideband monopole antenna in free space, over a copper plate, and over an artificial magnetic conductor (AMC) surface: (a) simulations and (b) measurements.
Ⅳ. Conclusion
A miniaturized AMC that uses the first and second resonance frequencies was introduced and tested for dual band operation. We achieved the desired miniaturization and easy control of the second/first resonant frequency ratio by inserting four slots in a symmetrical fashion into the metallic patch of the AMC unit cell. We demonstrated the dualband capability of the proposed AMC structure by suspending a wideband monopole over an AMC surface with resonance frequencies of approximately 2.45 and 5.2 GHz. The controllable frequency ratio, ease of fabrication, and miniaturized size of the proposed AMC structure support its potential use in dualband wireless communication.
Radiation patterns of a monopole antenna in free space and over an artificial magnetic conductor (AMC) surface: (a) simulations and (b) measurements. Eplane (AMC), Hplane (AMC), Eplane (free space), and Hplane (free space).
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