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Partial O-state Clamping PWM Method for Three-Level NPC Inverter with a SiC Clamp Diode
Partial O-state Clamping PWM Method for Three-Level NPC Inverter with a SiC Clamp Diode
Journal of Electrical Engineering and Technology. 2015. May, 10(3): 1066-1074
Copyright © 2015, The Korean Institute of Electrical Engineers
This is an Open-Access article distributed under the terms of the Creative Commons Attribution Non-Commercial License (http://creativecommons.org/licenses/by-nc/3.0/)which permits unrestricted non-commercial use, distribution, and reproduction in any medium, provided the original work is properly cited.
  • Received : June 20, 2014
  • Accepted : February 03, 2015
  • Published : May 01, 2015
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About the Authors
Nam-Joon Ku
Dept. of Electrical Engineering, Hanyang University, Korea. (aidmaku@hanyang.ac.kr)
Rae-Young Kim
Dept. of Electrical and Biomedical Engineering, Hanyang University, Korea. (rykim@hanyang.ac.kr)
Dong-Seok Hyun
Corresponding Author: Dept. of Electrical and Biomedical Engineering, Hanyang University, Korea. (dshyun@hanyang.ar.kr)

Abstract
This paper presents the reverse recovery characteristic according to the change of switching states when Si diode and SiC diode are used as clamp diode and proposes a method to minimize the switching loss containing the reverse recovery loss in the neutral-point-clamped inverter at low modulation index. The previous papers introduce many multiple circuits replacing Si diode with SiC diode to reduce the switching loss. In the neutral-point-clamped inverter, the switching loss can be also reduced by replacing device in the clamp diode. However, the switching loss in IGBT is large and the reduced switching loss cannot be still neglected. It is expected that the reverse recovery effect can be infrequent and the switching loss can be considerably reduced by the proposed method. Therefore, it is also possible to operate the inverter at the higher frequency with the better system efficiency and reduce the volume, weight and cost of filters and heatsink. The effectiveness of the proposed method is verified by numerical analysis and experiment results.
Keywords
1. Introduction
Because of a growing demand for higher efficiency, higher power density and higher temperature capability of the power converter, there has been a lot of effort in developing power semiconductor devices with Silicon Carbide (SiC) which has the better material properties, compared with them of Silicon [1 - 6] . SiC schottky diode is superior to Si diode in some characteristics, such as the high-breakdown voltage, the high temperature capability and almost zero reverse-recovery current [7 - 9] It is already verified that the SiC diode has extremely low reverse recovery current and low switching loss characteristics compared to those of the Si diode at the same forward current [10 , 11] . Many multiple circuits replacing Si diode with SiC diode for more improved performance is introduced in the recent studies [12 - 18] . The behavior of SiC diode in the circuit-level is analyzed by a thorough characterization [19 - 21] . The neutral-point-clamped (NPC) inverter using SiC diode as the clamp diode has already come into the market. The reverse recovery loss and the switching loss can be partly reduced by replacing Si diode with SiC diode in the clamp diode of NPC inverter. However, the switching loss in IGBT is quite large and the reverse recovery loss caused by the anti-parallel diode of IGBT still remains in the system. The reverse recovery current causes unwanted EMI noise in the circuit and additional efficiency reduction in the system [22 - 24] . In the worst case, the reverse recovery current has the excessive peak value, this current leads to the destruction of the switching devices.
This paper presents a performance comparison of a 3-level NPC inverter using Si and SiC clamp diodes and proposes the pulse with modulation (PWM) method to minimize the rest of the switching loss containing the reverse recovery loss by maximizing the reverse recovery characteristics of the SiC diode. The performance is evaluated by the reverse recovery characteristics, system efficiency and total harmonic distortion (THD). For the operation of NPC inverter at the higher switching frequency, SiC diode and IGBT which has the low switching energy are selected to prevent a severe increase in the switching loss. Instead of having the low switching energy, the IGBT device has the high forward voltage drop because there is usually a trade-off. When the proposed method is applied, there is the disadvantage that the conduction loss increases in the system. However, a decrease of switching loss is larger than an increase of conduction loss and the total loss is reduced in the inverter system. Therefore, the disadvantage is also covered by the proposed method.
It is expected that the proposed method is valuable to the applications required the high switching frequency operation with high efficiency and useful in reducing the volume, weight and cost of filters and heatsink. The effectiveness of the proposed PWM method is verified by the numerical calculation based on the performance evaluation of each device and experiment results.
2. A Comparison of the Reverse Recovery Characteristics in NPC Inverter
Fig. 1 shows a schematic diagram of a three-level NPC inverter. Each leg of the inverter consists of two clamped diodes, four IGBT and four anti-parallel diodes. The three-level inverter has three kinds of the switching states such as p, o and n in each leg. Table 1 shows the switching states and the output leg voltages of the three-level NPC inverter.
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The NPC 3-level inverter
Switching states of a three-level NPC inverter
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Switching states of a three-level NPC inverter
- 2.1 NPC Inverter with a Si clamp diode
In case of using Si diode as the clamp diode in NPC inverter presented in Fig. 1 , the reverse recovery effects occur whenever the switching states of NPC inverter change from a state, the clamp diode or the anti-parallel diode of IGBT is in the ON state, to the other states as presented in Fig. 2 . The reverse recovery effects cause the reverse recovery loss and the extra conduction loss due to the reverse recovery current, irr in Fig. 2 .
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The reverse recovery effects in NPC inverter with Si clamp diode
- 2.2 NPC inverter with a SiC clamp diode
In case of using SiC diode as the clamp diode in NPC inverter, there is no reverse recovery effect in the clamp diode due to the property of SiC diode. So the reverse recovery effects are quite reduced than the above case. The reverse recovery effects occur whenever the switching states of NPC inverter change from the P state or the N state, the anti-parallel diode of IGBT is in the ON state, to the O state. According to the direction of the load current, ix in Fig. 2 , it is decided whether the reverse recovery effects will occur or not. The only cases that the reverse recovery effects occur in NPC inverter using SiC diode are presented in Fig. 2 (a) , (b) .
The remained reverse recovery effects only occur when the reference voltage and the load current have the opposite sign each other. When the phase angle between reference voltage and load current is θ , the power factor is cos θ . In other words, as the power factor is smaller, the area where the reverse recovery effects occur becomes wider.
3. The Proposed Method
Fig. 3 shows the example comparing the Sinusoidal PWM(SPWM) method and the proposed method which adds the offset voltage to the reference voltages of each phase in the SPWM method when the power factor angle is about 36° (the power factor is about 0.8). There is a remarkable difference in the reverse recovery area.
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The comparison in the reverse recovery area
In Fig. 3 (a) , the reverse recovery effect always occurs during the whole period in the SPWM method with Si clamp diode.
In Fig. 3 (b) , when the switching states change from the O state to the P state or the N state, there is no reverse recovery effect due to the performance characteristics of the SiC diode. So, the single reverse recovery area is 36° in the SPWM method with SiC clamp diode. A section, in which the load current of a phase has the maximum amplitude, compared with the others, is arranged every 60° intervals in Fig. 3 . The single reverse recovery area in the SPWM method with SiC clamp diode overlaps with this area.
In Fig. 3 (c) , the single reverse recovery area is only 6° in the proposed method with SiC clamp diode and the load current is absolutely small in the reverse recovery area. So the remained reverse recovery losses are very small. If the power factor angle is smaller than 30° , the proposed method makes the reverse recovery loss to zero during the whole period.
In the proposed method, an offset voltage is added to the reference voltages of each output leg voltages ( Vu , Vv , Vw ). Because the reverse recovery area and the peak current area overlap each other and both the switching loss containing the reverse recovery loss and the conduction loss are a function of the load current [5] , the offset voltages added to the reference voltages are determined according to the magnitude of each load currents ( Iu , Iv , Iw ). Table 2 shows the offset voltage according to the condition. In Fig. 4 , new output leg voltages
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and
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are given by:
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The offset voltage according to the condition
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The offset voltage according to the condition
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The reference voltages and switching states
The modulation index is restricted to a low value under 0.5 because the magnitude of the reference voltage should be lower than the dc-link voltage. The reference voltage of the phase which has the maximum load current is clamped to the O rail in the section by adding the offset voltage. So, it is possible to reduce the reverse recovery loss and minimize the switching loss in IGBT by placing a phase, of which a load current has the maximum amplitude, on the O rail. Moreover, because there are no changes in the switching states when the phase is clamped to the O rail, the switching loss are perfectly eliminated.
4. Performance Evaluation
For the performance evaluation of the proposed method, the switching losses in the devices are compared when Si diode and SiC diode are used as clamp diode in NPC inverter. The experiment setup is shown in Fig. 5 and the setup information is shown in Table 3 and Table 4 . To calculate the switching loss, the switching energy losses of each device are measured by experiments.
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NPC 3-level inverter experiment setup
The experimental setup information
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The experimental setup information
The switch device information
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The switch device information
Fig. 6 and Fig. 7 present the turn ON/OFF characteristic examples of each device measured by experiments. Eon/off is approximately calculated by using the waveforms in Fig. 8 and (2)-(4).
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The reverse recovery characteristic of SiC diode and anti-parallel Si diode of IGBT
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The IGBT turn ON/OFF characteristic
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The switching energy loss of IGBT
where Eon/off is the switching ON/OFF energy loss, ton/off is the switching time, IF is the peak value of the forward current and k denotes an integer that means the switching number. When the output frequency is 60Hz and the switching frequency is 25kHz, k has the boundary between 0 and 416 (≅ 25k / 60).
The calculated switching energy is presented in Fig. 8 . The constant values m, n, p and q are obtained by using the trend line function of Excel. The constant values of clamp diode, m, n, p, and q in (3) and (4), are 0.00000458, 0.1566274225, 0.00000572 and 0.0330124878, respecttively. The constant values of IGBT are 0.00001094, 0.3571856833, 0.00023134 and 0.7988970686, respecttively. The constant values of anti-parallel diode are 0.00000626, 0.6550135871 and 0.00000754, respectively.
In each sampling time, the number of switch changing the switching state is two. In other words, ON and OFF operation in the single leg occur one in each sampling time. After calculating each Eon/off by using the obtained m, n, p and q, the switching loss in each sampling time is calculated by (5). Finally, ptotal is calculated by (6) with considering the area occurring the switching of each device during a period.
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where T is the switching period, p [ k ] is the average value of an instantaneous switching loss in a device and ptotal is the total average value of the switching loss in a device during one period. In (6), the star( ) means only k in the area occurring the switching of each device during a period.
The calculated switching loss in the clamp diode on each condition is shown in Table 5 . When Si diode is replaced by SiC diode under the SPWM method, the decreasing rate of the switching loss in the clamp diode is about 35%. In the proposed method, when Si diode is replaced by SiC diode, the decreasing rate of the switching loss in the clamp diode is about 57%.
The switching loss in a clamp diode
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The switching loss in a clamp diode
The calculated switching loss in each switch by each condition is shown in Table 6 , Table 7 and Table 8 . Because the switching loss in IGBT is greatly large, the effectiveness is small when Si diode is only replaced by SiC diode. However, the effectiveness is obvious in proposed method.
The switching loss in each switch (SPWM method and Si clamped diode)
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The switching loss in each switch (SPWM method and Si clamped diode)
The switching loss in each switch (SPWM method and SiC clamped diode)
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The switching loss in each switch (SPWM method and SiC clamped diode)
The switching loss in each switch (Proposed method and SiC clamped diode)
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The switching loss in each switch (Proposed method and SiC clamped diode)
The calculated total switching loss is shown in Table 9 . When using proposed method, the total switching loss reduction is about 7W, equivalently 31% of a total switching loss under general SPWM with Si clamping diode.
The total switching loss
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The total switching loss
Both the inverters using SiC clamp diode and using Si clamp diode were tested with a resistive-inductive load and experimental setup with the same procedure and the same conditions. For the load test, the output leads of the inverter are connected to a three-phase resistor and inductor in series. The DC-link voltage was 200 V and modulation index was varied from 0 to 1. The switching frequency is 20 kHz.
For each value of modulation index, input / output power, the dc-link voltage, dc-link current, output current, output voltage, efficiency and THD of output current were measured by power analyzer PPA5530 from Newtons 4th Ltd. Fig. 9 compares the inverter system efficiency measured in inverter using proposed method and that of conventional method at each modulation index. On average, 2.05 % loss reduction in inverter system using the proposed method is observed during the modulation index is varied from 0.2 to 0.7. After the modulation index is 0.8, the efficiency of inverter system using the conventional method is 0.87% higher on average because the correct offset voltage in Table 2 cannot be added to the reference voltages due to a restriction of the modulation index. The more a modulation index increases, when the output current has a maximum value, the more a section where the correct offset voltage is applied becomes narrow and the efficiency decreases.
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Inverter system efficiency curves for various modulation index.
The inverter operation waveforms, efficiency and THD for two different methods with different switching frequency are shown in Fig. 10 , Fig. 11 and Table 10 .
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Inverter reference voltage, pole voltage and load current during RL load test for two different methods: (a) Proposed method; (b) Conventional method; Vdc = 200V, iu, peak-to-peak = 3A and fsw = 20kHz.
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Inverter reference voltage, pole voltage and load current during RL load test for two different methods. (a) Proposed method, (b) Conventional method; Vdc = 200V, iu, peak-to-peak = 3A and fsw = 2kHz.
Efficiency and the output current THD of the inverter system using proposed method and conventional method with different switching frequency condition
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Efficiency and the output current THD of the inverter system using proposed method and conventional method with different switching frequency condition
There is a slight difference 0.2% between the efficiency on both methods at 2kHz switching frequency. In the case of 20kHz switching frequency, the gap widened up to 2.8%. Although the output current THD of proposed method is worse than that of conventional method due to a nonsinusoidal reference voltage, the value is allowable at high switching frequency.
It is verified through the experiment that the proposed method is more effective on high switching frequency and low modulation index condition.
5. Conclusion
In this paper, a partial O-state clamping PWM method for three-level NPC inverter using SiC diode as clamp diode. On three-level NPC inverter system replacing Si clamp diode with SiC clamp diode, the occurrence of the reverse recovery effects are compared according to the change of switching state. Because the occurrence frequency is significantly reduced by adding offset voltage to the reference voltage, the reverse recovery loss is reduced by proposed method. The switching loss is simultaneously reduced by clamping the reference voltage of one phase to the O rail in the section where the phase has the maximum load current. The switching energy loss of IGBT and the reverse recovery characteristics of each diode are measured by the repeated experiment and the switching losses of each device are compared in three cases. In comparison with conventional method, it is possible to reduce most of the switching loss in IGBT and the reverse recovery loss or eliminate the reverse recovery loss perfectly by using the proposed method. The validity of proposed method is verified by numerical analysis and the experiment results. Consequently, the proposed method is effective for operating three-level NPC inverter at the higher switching frequency with the improved efficiency.
BIO
Nam-Joon Ku He received the B.S. and M.S. degrees in electrical engineering from Hanyang University, Seoul, Korea, in 2010 and 2012, respectively, where he is currently working toward the Ph.D. degree. His research interests include the control and application of multilevel converters and high-voltage direct current transmission system.
Rae-Young Kim He received the B.S. and M.S. degrees from Hanyang University, Seoul, Korea, in 1997 and 1999, respectively, and the Ph.D. degree from Virginia Polytechnic Institute and State University, Blacksburg, in 2009, all in electrical engineering. From 1999 to 2004, he was a Senior Researcher at the Hyosung Heavy Industry R&D Center, Seoul, Korea. In 2009, he was a Postdoctoral Researcher at National Semiconductor Corporation, working on smart home energy management system. Since 2010, he has been with Hanyang University, where he is currently an Assistant Professor in the Department of Electrical and Biomedical Engineering. His research interests include modeling and control of power converter systems, soft-switching techniques, energy management systems in smart grid applications, power converter systems for renewable energies, and motor drive systems. Dr. Kim received the First Prize Paper Award at the IEEE Industry Applications Society (IAS) Annual Meeting in 2007. Since 2009, he has been a member of the IAS Industry Power Converters Committee, and also served as a Reviewer for the IEEE Transaction on Industrial Electronics and the IEEE Transaction on Industry Applications.
Dong-Seok Hyun He received the B.S. and M.S. degrees from Hanyang University, Seoul, Korea, in 1973 and 1978, respectively, and the Ph.D. degree from Seoul National University, Seoul, Korea, in 1986, all in electrical engineering. From 1976 to 1979, he was a Researcher with the Agency of Defense Development, Korea. From 1984 to 1985, he was a Research Associate in the Department of Electrical Engineering, University of Toledo, Toledo, OH, and from 1988 to 1989, he was a Visiting Professor in the Department of Electrical Engineering, Technical University of Munich, Germany. Since 1979, he has been with Hanyang University, where he is currently a Professor in the Department of Electrical and Biomedical Engineering. He is the author of more than 650 publications concerning electric machine design, high-power engineering, power electronics, and motor drives. His research interests include power electronics, motor drives, traction, and their control systems. Dr. Hyun is a member of the IEEE Power Electronics, Industrial Electronics, Industry Applications, and Electron Devices Societies. He is also a member of the Institution of Engineering and Technology, the Korean Institute of Power Electronics, and the Korean Institute of Electrical Engineers.
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