Induction cooking application with multiple loads need high power inverters and appropriate control techniques. This paper proposes an inverter configuration with buckboost converter for multiple load induction cooking application with independent control of each load. It uses one halfbridge for each load. For a given dc supply of V
_{DC}
, one more V
_{DC}
is derived using buckboost converter giving 2V
_{DC}
as the input to each halfbridge inverter. Series resonant loads are connected between the centre point of 2 V
_{DC}
and each halfbridge. The output voltage across each load is like that of a fullbridge inverter. In the proposed configuration, half of the output power is supplied to each load directly from the source and remaining half of the output power is supplied to each load through buckboost converter. With buckboost converter, each halfbridge inverter output power is increased to a fullbridge inverter output power level. Each halfbridge is operated with constant and same switching frequency with asymmetrical duty cycle (ADC) control technique. By ADC, output power of each load is independently controlled. This configuration also offers reduced component count. The proposed inverter configuration is simulated and experimentally verified with two loads. Simulation and experimental results are in good agreement. This configuration can be extended to multiple loads.
1. Introduction
Induction cooking is one of the several applications of induction heating. Induction heating method is a far better approach than other conventional methods. In conventional methods, the heat is transferred from heat source to load by conduction or radiation. In induction heating, the heat is developed inside the load due to generation of eddy currents at skin depth level from the surface
[1]
. In recent times, considerable progress is made in control schemes and inverter configurations. A typical arrangement of high frequency (HF) induction heating circuit is shown in
Fig. 1
.
Typical arrangement of high frequency induction heating resonant inverter
Resonant inverter is commonly used as a source of high frequency AC supply. The DC input to it is derived by rectifying the utility AC source. High frequency AC flowing in the load coil results in eddy currents induced in the vessel at skin depth level resulting in heating effect. The eddy currents produced in the load are concentrated in a peripheral layer at skin depth (
δ
), which is expressed as
where,
ρ
is electrical resistivity,
μ
is magnetic permeability, μr is relative magnetic permeability of the load material, and
f_{s}
is switching frequency of the inverter. Commonly used topologies for induction cooking application are quasi resonant, halfbridge, and full bridge inverters
[2

4]
. Out of these, full bridge inverter is preferred for high power applications. Halfbridge inverter is preferred for less components count. Multipleload halfbridge series resonant inverter is shown in
Fig. 2
.
Multipleload halfbridge series resonant inverter
In this, L
_{r1}
is the coil inductance, C
_{r1}
is the resonant capacitance, and R
_{eq1}
is equivalent resistance of the load1. Similarly, L
_{r2}
, C
_{r2}
, and R
_{eq2}
are the coil inductance, resonant capacitance, and equivalent resistance of the load 2 respectively. C
_{1}
and C
_{2}
are DC link split capacitors. Q
_{1}
and Q
_{2}
are the switching devices with antiparallel diodes D
_{1}
and D
_{2}
of load1 inverter circuit. Q
_{3}
and Q
_{4}
are the switching devices with antiparallel diodes D
_{3}
and D
_{4}
of load2 inverter circuit. V
_{DC}
is the supply voltage,
i
_{1}
is the load1 resonant tank current and
i
_{2}
is the load2 resonant tank current.
Pulse amplitude modulation (PAM) and pulse frequency modulation (PFM) were used to control output power in induction heating application. Under PAM control, amplitude of the source voltage is varied to control the output power
[5]
. It requires power processing at two stages i.e., one at AC to DC power conversion and other at high frequency inverter, resulting in more complexity and reduced efficiency. Under PFM control, the switching frequency has to be varied over a wide range
[6]
. Also, the soft switching operating region for zero voltage switching (ZVS) operation is relatively narrow. If the circuit operates below the resonance, the filter components are large at low frequency range. In
[7]
, for induction heating application, phase shift control (PSC) technique is used for output power control. ZVS problem is minimized by varying the switching frequency. In
[8]
, phaseshifted PWM and loadadaptive PFM control strategies are used. In [9], hybrid power control technique with pulse density modulation (PDM) and phaseshift modulation (PSM) are proposed for induction heating applications. These methods improve the performance of the inverter in several aspects. ZVS problem is also minimized by techniques such as asymmetrical voltage cancellation (AVC) and asymmetrical duty cycle (ADC) control
[10]
. In
[11]
, two operating modes for power control of halfbridge resonant inverter induction heating system are described. One operating mode uses variable frequency control for larger output power. Other operating mode uses pulse density modulation control in low to medium power range. It has the advantage of high efficiency over wide output power range. The limitation is the use of variable frequency control in certain power range.
In induction cooking application, one inverter feeds power to a single load. For multiple load application, there is a need to develop inverter circuits and control techniques which can minimize components count and provide independent control of each load. Certain techniques are available in the literature. In
[12]
, single inverter with two load system is proposed and analyzed. It uses variable switching frequency control. This scheme has one master load and one slave load. It has several resonant capacitors connected in parallel by electromechanical switches. These are activated for power control. In
[13]
, an inverter configuration for two loads is suggested. It has three legs wherein one leg is common for both the loads. This configuration provides independent and simultaneous control of both loads. Asymmetric voltage cancellation technique is used for control of the inverters. This method has the advantage of reduced components count and better utilization of devices. This technique can be extended to more than two loads also. In
[14]
, twooutput charge boost type induction cooking application is proposed using asymmetrical voltage cancellation technique. A power factor correction stage is also added to improve the power factor. In
[15]
, a loadadaptive control algorithm for variable load and large output power range is proposed and described. In the design process, aspects like efficiency, acoustic noise, and flicker emissions are considered. It is shown that single control strategy is not suitable when several aspects are to be considered. An appropriate combination of different control techniques is suggested for each power range. The limitation of this method is increased complexity in the control implementation. In
[16]
, a costeffective multipleload system is proposed. It uses discontinuous mode control to improve lightload performance. Converter efficiency is increased by reducing switching frequency while maintaining proper power factor. Switching frequency range is between 20 to 150 kHz. Variable switching frequency is the limitation of this method. In
[17]
, systemonprogrammable chip and FPGA based test bench for multiple inductor power converter is proposed. The power converter is modelled in VHDL. This speedsup the simulation process of the system. In
[18]
, multiple output induction heating system which uses direct acac power conversion is proposed. This method gives higher efficiency, reduced components count and reduced complexity. This is achieved with the use of matrix converter for multiple loads. Variable frequency control may be the limitation of this method. Also, larger input harmonic currents are present under unbalanced operation.
This paper proposes buckboost interleaved inverter configuration for induction cooking application with multipleloads. It uses one halfbridge for each load. For a given dc supply of V
_{DC}
one more V
_{DC}
is derived using buckboost converter giving 2V
_{DC}
as the input to each halfbridge. Series resonant loads are connected between the centre point of 2V
_{DC}
and each halfbridge. Output voltage is switched between +V
_{DC}
and –V
_{DC}
with halfbridge configuration. In the proposed configuration, half of the output power is supplied to each load directly from the source and remaining half of the output power is supplied frequency with ADC control technique. By ADC
[9]
, output power of each load is independently controlled. The proposed configuration can be extended to multipleloads. to each load through buckboost converter. With buckboost converter, each halfbridge inverter output power is increased to a fullbridge inverter output power level. Each halfbridge is operated with constant and same switching
2. Proposed Inverter Configuration
This section describes the proposed inverter configuration for multipleload induction cooking application. Circuit diagram of the proposed inverter is shown in
Fig. 3
for two loads. Both loads use series resonant circuit. It uses one halfbridge for each load. For a given dc supply of V
_{DC}
one more V
_{DC}
is derived using buckboost converter giving 2V
_{DC}
as the input to each halfbridge. Due to polarity reversing nature of output voltage in buckboost converter, it becomes possible to use input and output voltages of buckboost converter as two dc sources like split capacitor configuration of halfbridge inverter. With suitable duty ratio of buckboost converter, it is possible to maintain output voltage equal to input voltage (V
_{DC}
) for all induction heating loads. Hence, input and output voltages of buckboost converter are maintained at equal magnitude. This gives total input voltage of 2V
_{DC}
to each halfbridge inverter, which is also a series connection of two dc sources each of V
_{DC}
. The buckboost converter is switched at 30 kHz.
Proposed inverter configuration for multipleload induction cooking
Series resonant loads are connected between the centre point of 2V
_{DC}
and each halfbridge as shown in
Fig. 3
. The output voltage across each load switches between +V
_{DC}
and –V
_{DC}
with halfbridge configuration. It is similar to that of a full bridge inverter with V
_{DC}
as the DC input. Hence in this proposed configuration, each load handles same power as that supplied from a fullbridge configuration. Each halfbridge is operated with constant and same switching frequency with ADC control technique. By ADC, output power of each load is independently controlled. Load1 is connected to inverter output voltage
ν
_{AB}
. Load2 is connected to inverter output voltage
ν
_{AC}
. Load1 consists of C
_{r1}
, L
_{r1}
, and Req1 which are resonant capacitance, inductance and equivalent load resistance respectively making series resonant tank. Similarly, load2 consists of C
_{r2}
, L
_{r2}
, and R
_{eq2}
, which are resonant capacitance, inductance and equivalent load resistance respectively making series resonant tank. Resonant frequencies of two load circuits are f
_{r1}
=
and f
_{r2}
=
respectively. If required they can be of different power ratings, but operated at same switching frequency. Hence, the resonant frequencies of both load circuits have to be same.
In this paper, both loads have same component values and their resonant frequencies are same. L
_{r1}
= L
_{r2}
= L
_{r}
, C
_{r1}
= C
_{r2}
= C
_{r}
, and R
_{eq1}
= R
_{eq2}
= R
_{eq}
. Hence, their power rating is same and operated at a switching frequency of 30 kHz. Resonant frequency of each load circuit is, f
_{r}
=
Switching frequency of each leg is slightly higher than their resonant frequency. Hence, inverter switching frequency (f
_{s}
) can be chosen 5 to 10% higher than the resonant frequency (f
_{r}
) for ZVS operation.
Fig. 4
shows gating signals
ν
_{g1}
and
ν
_{g2}
for the switching devices Q
_{1}
and Q
_{2}
of halfbridge inverter for load1. Also, output voltage (
ν
_{AB}
) along with its fundamental component (
ν
_{AB1}
) is shown. The load1 current (
i
_{1}
) is shown assuming it to be sine wave due to filtering of harmonics by resonant load. These waveforms are based on ADC control technique. Here, the angles θ
_{1}
or β
_{1}
can be used as control variables and β
_{1}
= (180° – θ
_{1}
). Ø
_{1}
is the angle between vAB1 and
i
_{1}
. β
_{1}
can be controlled to control the dutyratio of output voltage (
ν
_{AB}
). The dutyratio (D
_{1}
) of load1 halfbridge inverter is defined as
Output voltage and current with control variables with ADC control technique
In
Fig. 4
, T
_{on}
and T/2 are shown with gating pulses for load1 halfbridge inverter. Analysis of asymmetrical duty cycle control for series resonant inverter is presented in
[10]
. Harmonics in load current waveform are negligibly small and ignored.
The amplitude of the fundamental voltage
can be expressed in ADC control technique as,
is the amplitude of the load1 current and assumed to be sinusoidal. The phase lag Ø
_{1}
between the voltage
ν
_{AB1}
and the load current
i
_{1}
can be expressed as,
The quality factor (Q) and normalized switching frequency ( ω
_{n}
) are defined as
where ω
_{s}
is angular switching frequency and ω
_{r}
is angular resonant frequency.
The resonant tank circuit current (
) is expressed as,
where Ø = Ø
_{1}
The load1 output power can be expressed as,
where P
_{o2}
is output power of load2 and θ
_{2}
is control variable for load2. The total output power (P
_{T}
) is expressed as P
_{T}
= P
_{o1}
+ P
_{o2}
. From the above equations, the amplitude of individual currents and output powers can be controlled by varying corresponding control angles θ
_{1}
and θ
_{2}
. As θ
_{1}
and θ
_{2}
can be independently controlled, both loads are independently controllable.
The output voltage across each load is like that of a fullbridge inverter. Hence the output power increases with proposed configuration. In the proposed configuration, half of the output power is supplied to each load directly from the source and remaining half of the output power is supplied to each load through buckboost converter.
The buckboost converter shown in
Fig. 3
needs to be controlled in closed loop to maintain its output voltage equal to input voltage under different load conditions. Since, half of the load power is processed through buckboost converter, losses in buckboost converter have to be minimized as much as possible. This helps in improving overall efficiency of the proposed configuration. For this, in place of freewheeling diode power MOSFET (S
_{2}
) is used. This reduces losses during freewheeling. Also, both MOSFETs used in buckboost converter are of low onstate resistance.

For, Pin= inverter input, and PT= total inverter output

ηI= inverter efficiency =

ηB= efficiency of buckboost converter

η = overall efficiency (with buckboost converter)
Overall efficiency is dependent on η
_{B}
. For ideal buckboost converter, η
_{B}
=1 and η = η
_{I}
. Under practical condition, η
_{B}
is less than unity. This results in η < η
_{I}
.
3. Results of Proposed Inverter Configuration
Experimental setup of proposed inverter configuration is shown in
Fig. 5
.
Experimental setup of proposed inverter configuration
Proposed inverter configuration with ADC control technique is simulated and experimentally verified using the parameters shown in
Table 1
.
Parameters of proposed inverter configuration for induction cooking
Parameters of proposed inverter configuration for induction cooking
Proposed circuit of halfbridge series resonant inverter configuration for two load induction cooking application is designed and operated at a switching frequency of 30 kHz. It is for a total output power (P
_{T}
) of 135 watts with a source voltage of 15V. The simulation and experimental studies are done for different dutyratio combinations of D
_{1}
and D
_{2}
. D
_{1}
and D
_{2}
are dutyratios of inverter output voltages ν
_{AB}
and ν
_{AC}
respectively. Gate pulses, inverter output voltage waveforms and load currents for the proposed inverter configuration are shown in
Figs. 6
to
9
for various dutyratio combinations.
Inverter waveforms for D_{1}= 0.97 and D_{2}= 0.97
Inverter waveforms for D_{1}= 0.97 and D_{2}= 0.6
Inverter waveforms for D_{1}= 0.7 and D_{2}= 0.3
Inverter waveforms for D_{1}= 0.5 and D_{2}= 0.3
Figs. 6(a)
,
7(a)
,
8(a)
, and
9(a)
show gate pulses
ν
_{g1}
to
ν
_{g4}
of switching devices Q
_{1}
to Q
_{4}
for various dutyratio combinations of D
_{1}
and D
_{2}
. These figures also show inverter output voltages
ν
_{AB}
and
ν
_{AC}
for these dutyratio combinations.
Fig. 6(a)
shows these waveforms for D
_{1}
= 0.97 and D
_{2}
= 0.97.
Figs. 7(a)
,
8(a)
, and
9(a)
show them for D
_{1}
= 0.97 and D
_{2}
= 0.6, D
_{1}
= 0.7 and D
_{2}
=0.3, and D
_{1}
=0.5 and D
_{2}
=0.3 respectively. These figures help in understanding the operation of the proposed inverter configuration.
Fig. 6(b)
shows the simulation waveforms of both inverter output voltages and their load currents for a dutyratio of D
_{1}
= 0.97 and D
_{2}
= 0.97.
Figs. 7(b)
,
8(b)
, and
9(b)
show them for D
_{1}
= 0.97 and D
_{2}
= 0.6, D
_{1}
= 0.7 and D
_{2}
= 0.3, and D
_{1}
= 0.5 and D
_{2}
= 0.3 respectively. Similarly,
Fig. 6(c)
shows these waveforms of inverter output voltages and their load currents under experimental condition. In
Fig. 6(c)
, D
_{1}
= 0.97 and D
_{2}
= 0.97.
Figs. 7(c)
,
8(c)
, and
9(c)
show them for D
_{1}
= 0.97 and D
_{2}
= 0.6, D
_{1}
= 0.7 and D
_{2}
=0.3, and D
_{1}
= 0.5 and D
_{2}
= 0.3 respectively.
From
Figs. 6
to
9
, it can be observed that each output voltage waveform and its load current is independently controlled with ADC control technique. Independent control is achieved by variation of dutyratios of individual inverters. This gives power control in each load independently.
From simulation and experimental results, it is observed that both results are in good agreement with each other. It is also seen that for a given DC input voltage of V
_{DC}
, the proposed inverter configuration of halfbridge series resonant inverter has same output voltage level as fullbridge configuration. This concept can be extended for multipleloads also. Here, all loads can be operated at same switching frequency. In
Figs. 6
and
7
, dutyratio of load2 is 0.97 and 0.6 respectively, whereas dutyratio of load1 is kept constant at 0.97. It can be observed that current in load2 varies with the variation of its dutyratio, while the current in load1 remains constant. Hence, current in load2 is controlled independently. Similarly, in
Figs. 8
and
9
, dutyratio of load1 is 0.7 and 0.5 respectively, whereas dutyratio of load2 is kept constant at 0.3. It can be observed that current in load1 varies with variation of its dutyratio while the current in load2 remains constant. Hence, current in load1 is controlled independently. Proposed inverter configuration gives advantage of independent power control of each load. Though each load is powered with halfbridge configuration, it has output power capability of fullbridge. Also, it reduces component count for multiple loads.
In this paper, the switching frequency used for inverters is 30 kHz. Hence, ZVS is not of much concern. If required, the inverters can be switched at higher frequencies with possibility of ZVS.
4. Independent Control of Load Power
Load power control is achieved using ADC control technique. Output powers of load1 and load2 are dependent on corresponding load currents. In
Table 2
, load 1 current is controlled with its dutyratio, and load2 current remains constant as D
_{2}
is kept constant at 0.97.
Load1 current with its dutyratio
Load1 current with its dutyratio
Similarly, it can be shown that when load2 current varies with its dutyratio and load1 current remains constant. Each load current is controlled independently with its dutyratio. It can be observed from
Figs. 10
and
11
.
Variation of current in load1 vs. D_{1}
Variation of current in load2 vs. D_{2}
Variation of current in load1 with variation of D
_{1}
is shown in
Fig. 10
. For this, D
_{2}
is kept constant at 0.97. Under this condition, current in load1 only varies whereas current in load2 remains constant. Similarly, variation of current in load2 with variation of D
_{2}
is shown in
Fig. 11
. For this, D
_{1}
is kept constant at 0.97. Under this condition, current in load2 only varies whereas current in load1 remains constant. Simulation and experimental results are in good agreement with each other.
In
Fig. 12
, variation of output power of load1 vs. D
_{1}
is shown with proposed configuration and with conventional halfbridge configuration. In the proposed configuration, output power is 4 times compared to conventional halfbridge configuration.
Variation of output power for load1 vs. D_{1}
5. Overall Efficiency
Overall efficiency for the proposed configuration is shown in
Fig. 13
. In
Fig. 13
, output power of load1 is controlled while that of load2 is kept constant at its maximum. Total output power is measured by addition of individual inverter outputs. Each inverter output is computed as I
^{2}
R
_{eq}
. ‘I’ is the r.m.s current value of individual load circuit. ‘R
_{eq}
’ is the equivalent load resistance of each load. Input power is obtained by multiplication of dc input voltage (V
_{DC}
) and average current of the source. Overall efficiency includes the efficiency of buckboost converter also. To maintain high overall efficiency, buckboost converter also should have high efficiency. It should be taken care in design stage.
Overall efficiency vs. D_{1}
Both of the loads are of same power capacity. Hence, overall efficiency characteristic will be same if output power of load1 is kept constant and that of load2 is varied. Under fullload condition, overall efficiency is > 93%.
6. Conclusions
In this paper, buckboost interleaved inverter configuration with halfbridge series resonant inverters for twoload induction cooking application has been proposed. In this configuration, each halfbridge inverter output power is increased to a fullbridge inverter output power level. Both loads are independently controlled. It can be extended for more than two loads also. Excluding buckboost converter, number of switching devices/load is two i.e., one leg/load. Same switching frequency is used for powering both the loads. i.e., each load is operated at same switching frequency of 30 kHz. Asymmetric duty cycle control technique is used for power control of individual loads. Under fullload condition, overall efficiency is >93%. Design and control of the proposed configuration are simple. Simulation and experimental results of the proposed configuration are in good agreement.
BIO
P. Sharath Kumar He received B.Tech degree in Electrical and Electronics Engineering from Jawaharlal Nehru Technological University, Hyderabad, India in 2006 and M.Tech degree from National Institute of Technology, Kurukshetra, India in 2008. Presently pursuing Ph.D in Electrical Engineering at National Institute of Technology, Warangal, India. His area of interest is high frequency resonant inverters.
N. Vishwanathan He received B.Sc (Engg.) degree in electrical engineering from Dayalbagh Educational Institute, Agra, India, in 1990, M.Tech. degree in electrical machines and industrial drives from REC, Warangal, India in 1992, and Ph.D. from Indian Institute of Science, Bangalore, India, in 2004. He is currently working as Professor in the Dept. of Electrical Engg, NIT, Warangal, India. His areas of interest are switched mode power conversion and induction heating applications.
Bhagwan K. Murthy He obtained his B.E. (Electrical) and M.E. (Industrial Electronics) degrees from the M. S. University of Baroda, India in 1983 and 1987, respectively. He did his PhD at IIT Madras in 1999. He is working as Professor of Electrical Engineering in the National Institute of Technology, Warangal, India. His research interests include application of power electronics to DSP controlled industrial drives and renewable energy.
Moreland W. C.
1973
“The induction range: Its performance and its development problems,”
IEEE Trans. Industry Applications
IA9
(1)
81 
85
DOI : 10.1109/TIA.1973.349892
Miyamae Masaki
,
Ito Takahiro
,
Matsuse Kouki
,
Tsukahara Masayoshi
2012
“Performance of a High Frequency QuasiResonant Inverter with VariableFrequency Output for Induction Heating”
IEEE 7th International Power Electronics and Motion Control Conference
Harbin, China
Kamli Mokhtar
,
Yamamoto Shigehiro
,
Abe Minoru
1996
“A 50150 kHz HalfBridge Inverter for Induction Heating Applications,”
IEEE Trans. Industrial Electronics
43
(1)
163 
172
DOI : 10.1109/41.481422
Ahmed S.M.W.
,
Eissa M.M.
,
Edress M.
,
AbdelHameed T.S.
“Experimental investigation of fullbridge Series Resonant Inverters for InductionHeating Cooking Appliances”
4th IEEE Conference on Industrial Electronics and Applications, ICIEA 2009
3327 
3332
Okuno Atsushi
,
Kawano Hitoshi
,
Sun Junming
,
Kurokawa Manabu
,
Kojina Akira
,
Nakaoka Mutsuo
1998
“Feasible Development of SoftSwitched SIT Inverter with LoadAdaptive Frequency Tracking Control Scheme for Induction Heating,”
IEEE Trans. Industry Applications
34
(4)
713 
718
DOI : 10.1109/28.703962
Kwon YoungSup
,
Yoo SangBong
,
Hyun DongSeok
1999
“HalfBridge Series Resonant Inverter for Induction Heating Applications with LoadAdaptive PFM Control Strategy”
14th Applied Power Electronics Conference and Exposition, APEC’ 99
1
575 
581
Grajales L.
,
Sabate J. A.
,
Wang K. R.
,
Tabisz W. A.
,
Lee F.C.
1993
“Design of a 10 kW, 500 kHz PhaseShift Controlled SeriesResonant Inverter for Induction Heating”
Industry Applications Society Annual Meeting
2
843 
849
Nagai Satoshi
,
Nagura Hirokazu
,
Nakaoka Mutsuo
,
Okuno Atsushi
1993
“HighFrequency Inverter with PhaseShifted PWM and LoadAdaptive PFM Control Strategy for Industrial InductionHeating”
Industry Applications Society Annual Meeting
3
2165 
2172
Shen Jinfei
,
Ma Hongbin
,
Yan Wenxu
,
Hui Jing
,
Wu Lei
“PDM and PSM Hybrid Power Control of a SeriesResonant Inverter for Induction Heating Applications”
IEEE Conference on Industrial Electronics and Applications, ICIEA 2006
Burdio J. M.
,
Barragan L. A.
,
Monterde F.
,
Navarro D.
,
Acero J.
2004
“Asymmetrical voltage cancellation control for fullbridge series resonant inverters,”
IEEE Trans. Power Electronics
19
(2)
461 
469
DOI : 10.1109/TPEL.2003.823250
Sarnago Hector
,
Lucia Oscar
,
Mediano Arturo
,
Burdio J.M.
2013
“Class D / DE DualModeOperation Resonant Converter for ImprovedEfficiency Domestic Induction Heating System,”
IEEE Transactions on Power Electronics
28
(3)
1274 
1285
DOI : 10.1109/TPEL.2012.2206405
Forest F.
,
Laboure E.
,
Costa F.
,
Gaspard J.Y.
2000
“Principle of a multiload / single converter system for low power induction heating,”
IEEE Trans. Power Electronics
15
(2)
223 
230
DOI : 10.1109/63.838094
Burdio Jose M.
,
Monterde Fernando
,
R. Garcia Jose
,
Barragan Luis A.
,
Martinez Abelardo
2005
“A TwoOutput SeriesResonant Inverter for InductionHeating Cooking Appliances,”
IEEE Trans. Power Electronics
20
(4)
815 
822
Zenitani S.
,
Okamoto M.
,
Hiraki E.
,
Tanaka T.
2010
“A Charge Boost Type Multi Output FullBridge High Frequency Soft Switching Inverter for IH Cooking Appliance,”
14th International Power Electronics and Motion Control Conference (EPEPEMC)
T2127 
T2133
Lucia Oscar
,
Burdio J.M.
,
Millan I.
,
Acero J.
,
Puyal D.
2009
“LoadAdaptive Control Algorithm of HalfBridge Series Resonant Inverter for Domestic Induction Heating,”
IEEE Transactions on Industrial Electronics
56
(8)
3106 
3116
Lucia Oscar
,
Burdio Jose M.
,
Barragan Luis A.
,
Carretero Claudio
,
Acero Jesus
2011
“Series Resonant Multiinverter with DiscontinuousMode Control for Improved LightLoad Operation,”
IEEE Transactions on Industrial Electronics
58
(11)
5163 
5171
DOI : 10.1109/TIE.2011.2126541
Lucia Oscar
,
Urriza I.
,
Barragan Luis A.
,
Navarro D.
,
Jimenez Oscar
,
Burdio J.M.
2011
“Real Time FPGABased HardwareintheLoop Simulation Test Bench Applied to MultipleOutput Power Converters,”
IEEE Transactions on Industry Applications
47
(2)
853 
860
DOI : 10.1109/TIA.2010.2102997
Lucia Oscar
,
Carretero Claudio
,
Burdio J.M.
,
Acero Jesus
,
Almazan Fernando
2012
“MultipleOutput Resonant Matrix Converter for Multiple Induction Heaters,”
IEEE Transactions on Industry Applications
48
(4)
1387 
1396
DOI : 10.1109/TIA.2012.2199456